Transmission line transformer and amplifying circuit

ABSTRACT

A first transmission line and a second transmission line that are connected in series to each other are disposed at different positions in a thickness direction of a substrate. A third transmission line is disposed between the first transmission line and the second transmission line in the thickness direction of the substrate. The third transmission line includes a first end portion connected to one end portion of the first transmission line, and a second end portion that is AC-grounded. The first transmission line and the second transmission line are electromagnetically coupled to the third transmission line.

CROSS REFERENCE TO RELATED APPLICATIONS

This application is a continuation-in-part of U.S. patent applicationSer. No. 16/550,493 filed on Aug. 26, 2019, which claims priority fromJapanese Patent Application No. 2018-164417 filed on Sep. 3, 2018, andwhich claims priority from Japanese Patent Application No. 2019-112969filed on Jun. 18, 2019. The contents of these applications areincorporated herein by reference in their entireties.

BACKGROUND OF THE DISCLOSURE Field of the Disclosure

The present disclosure relates to a transmission line transformer and anamplifying circuit.

Description of the Related Art

There has been available a technique of using a transmission linetransformer as an impedance matching circuit that is disposed between anoutput terminal of an amplifier and a load (U.S. Pat. No. 8,384,484).The transmission line transformer disclosed in U.S. Pat. No. 8,384,484is constituted by two broadside-coupled transmission lines. In theconfiguration disclosed in U.S. Pat. No. 8,384,484, a plurality oftransmission line transformers are cascade-connected to achieve adesired impedance transformation ratio. A basic transmission linetransformer is described in “Chapter Six Transmission LineTransformers”, Radio Frequency Circuit Design, Second Edition, by W.Alan Davis, Copyright (C) 2011 John Wiley & Sons, Inc.

BRIEF SUMMARY OF THE DISCLOSURE

In the configuration disclosed in U.S. Pat. No. 8,384,484, a pluralityof transmission line transformers are cascade-connected to achieve adesired impedance transformation ratio because it is difficult toachieve a large impedance transformation ratio with a singletransmission line transformer. This configuration leads to difficulty inreducing the size of the impedance matching circuit.

An object of the present disclosure is to provide a transmission linetransformer capable of achieving a larger impedance transformation ratiothan that in a transmission line transformer according to the relatedart. Another object of the present disclosure is to provide anamplifying circuit including the transmission line transformer.

According to preferred embodiments of the present disclosure, atransmission line transformer includes: a first transmission line and asecond transmission line that are disposed at different positions in athickness direction of a substrate and that are connected in series toeach other; and a third transmission line that is disposed between thefirst transmission line and the second transmission line in thethickness direction of the substrate, that includes a first end portionconnected to one end portion of the first transmission line, and thatincludes a second end portion that is AC-grounded. The firsttransmission line and the second transmission line areelectromagnetically coupled to the third transmission line.

According to other preferred embodiments of the present disclosure, anamplifying circuit includes: an amplifying element that amplifies ahigh-frequency signal; and a transmission line transformer connected toan input terminal of the amplifying element or an output terminal of theamplifying element. The transmission line transformer includes: a firsttransmission line and a second transmission line that are disposed atdifferent positions in a thickness direction of a substrate and that areconnected in series to each other; and a third transmission line that isdisposed between the first transmission line and the second transmissionline in the thickness direction of the substrate, that includes a firstend portion connected to one end portion of the first transmission line,the one end portion being connected to the amplifying element, and thatincludes a second end portion that is AC-grounded. The firsttransmission line and the second transmission line areelectromagnetically coupled to the third transmission line.

According to other preferred embodiments of the present disclosure, atransmission line transformer includes: a substrate; and a firsttransmission line group and a second transmission line group that aredisposed in the substrate. The first transmission line group and thesecond transmission line group each include a main line and a sub line.The main line of each of the first transmission line group and thesecond transmission line group includes a first line and a second linethat are disposed at different positions in a thickness direction of thesubstrate. The sub line of the first transmission line group is disposedbetween the first line and the second line of the first transmissionline group in the thickness direction of the substrate. The sub line ofthe second transmission line group is disposed between the first lineand the second line of the second transmission line group in thethickness direction of the substrate. The first line, the second line,and the sub line of the first transmission line group include portionsoverlapping each other in plan view. The first line, the second line,and the sub line of the second transmission line group include portionsoverlapping each other in plan view. The sub line of the firsttransmission line group is electromagnetically coupled to each of thefirst line and the second line of the first transmission line group. Thesub line of the second transmission line group is electromagneticallycoupled to each of the first line and the second line of the secondtransmission line group. The sub line of the first transmission linegroup includes a first end portion connected to a first end portion ofthe main line of the second transmission line group, the first endportions corresponding to each other. The sub line of the secondtransmission line group includes a first end portion connected to afirst end portion of the main line of the first transmission line group,the first end portions corresponding to each other. The sub line of thefirst transmission line group includes a second end portion opposite tothe first end portion of the sub line of the first transmission linegroup. The sub line of the second transmission line group includes asecond end portion opposite to the first end portion of the sub line ofthe second transmission line group. The transmission line transformerincludes a connection structure that connects the second end portion ofthe sub line of the first transmission line group and the second endportion of the sub line of the second transmission line group to eachother.

An impedance transformation ratio larger than that in the related artcan be obtained by using a single transmission line transformer. Thus,an impedance matching circuit constituted by the transmission linetransformer can be reduced in size.

Other features, elements, characteristics and advantages of the presentdisclosure will become more apparent from the following detaileddescription of preferred embodiments of the present disclosure withreference to the attached drawings.

BRIEF DESCRIPTION OF THE SEVERAL VIEWS OF THE DRAWINGS

FIG. 1A is a schematic diagram for describing the operation principle ofa transmission line transformer according to a first embodiment;

FIG. 1B is a schematic perspective view of the transmission linetransformer according to the first embodiment;

FIG. 1C is a cross-sectional view taken along a dot-and-dash line 1C inFIG. 1B;

FIG. 2A is a diagram illustrating an example of a coil pattern;

FIG. 2B is a graph illustrating the relationship between a path lengthand a Euclidean distance at each point from an origin point to an endpoint E of the coil pattern;

FIG. 3A is a schematic diagram for describing the operation principle ofa transmission line transformer according to a second embodiment;

FIG. 3B is a schematic perspective view of the transmission linetransformer according to the second embodiment;

FIG. 4 is a schematic perspective view of a transmission linetransformer according to a modification example of the secondembodiment;

FIG. 5A is a schematic diagram for describing the operation principle ofa transmission line transformer according to a third embodiment;

FIG. 5B is a schematic perspective view of the transmission linetransformer according to the third embodiment;

FIG. 6 is a schematic perspective view of a transmission linetransformer according to a modification example of the third embodiment;

FIG. 7 is an equivalent circuit diagram of an amplifying circuitaccording to a fourth embodiment;

FIG. 8 is an equivalent circuit diagram of an amplifying circuitaccording to a fifth embodiment;

FIG. 9 is an equivalent circuit diagram of an amplifying circuitaccording to a sixth embodiment;

FIG. 10 is a block diagram of an amplifying circuit according to aseventh embodiment;

FIGS. 11A and 11B are block diagrams of impedance transformationcircuits according to an eighth embodiment as simulation targets;

FIGS. 12A and 12B are graphs obtained by plotting the trajectories ofimpedances (FIGS. 11A and 11B) at various frequencies on Smith charts;

FIGS. 13A and 13B are graphs illustrating simulation results ofinsertion loss of a transmission line transformer;

FIGS. 14A and 14B are block diagrams of impedance transformationcircuits according to a ninth embodiment as simulation targets;

FIGS. 15A and 15B are graphs obtained by plotting the trajectories ofimpedances (FIGS. 14A and 14B) at various frequencies on Smith charts;

FIGS. 16A and 16B are graphs illustrating simulation results ofinsertion loss of a transmission line transformer;

FIG. 17 is an equivalent circuit diagram of an amplifying circuitaccording to a tenth embodiment;

FIG. 18 is a plan view illustrating conductor patterns disposed in afirst layer of the amplifying circuit according to the tenth embodiment;

FIG. 19 is an exploded perspective view of a plurality of conductorlayers provided in a substrate used for the amplifying circuit accordingto the tenth embodiment;

FIG. 20 is an equivalent circuit diagram of an amplifying circuitaccording to an eleventh embodiment;

FIG. 21 is a schematic diagram for describing the operation principle ofa transmission line transformer according to a twelfth embodiment;

FIG. 22 is an exploded perspective view of the transmission linetransformer according to the twelfth embodiment;

FIG. 23 is a diagram illustrating the positional relationship ofmetallic patterns of the transmission line transformer according to thetwelfth embodiment in plan view;

FIG. 24 is an equivalent circuit diagram of the transmission linetransformer according to the twelfth embodiment;

FIG. 25 is an equivalent circuit diagram of an amplifying moduleaccording to a thirteenth embodiment;

FIG. 26 is an equivalent circuit diagram of an amplifying moduleaccording to a modification example of the thirteenth embodiment; and

FIG. 27 is an equivalent circuit diagram of an amplifying moduleaccording to another modification example of the thirteenth embodiment.

DETAILED DESCRIPTION OF THE DISCLOSURE First Embodiment

A transmission line transformer according to a first embodiment will bedescribed with reference to FIGS. 1A, 1B, and 1C.

FIG. 1A is a schematic diagram for describing the operation principle ofa transmission line transformer 20 according to the first embodiment.The transmission line transformer 20 according to the first embodimentincludes a first transmission line 21, a second transmission line 22,and a third transmission line 23 that are disposed on a surface of asubstrate or inside the substrate. The vertical direction in FIG. 1Acorresponds to the thickness direction of the substrate. The firsttransmission line 21 and the second transmission line 22 are disposed atdifferent positions in the thickness direction of the substrate. Thethird transmission line 23 is disposed between the first transmissionline 21 and the second transmission line 22 in the thickness directionof the substrate.

One end portion of the third transmission line 23 is referred to as afirst end portion 23A, and the other end portion thereof is referred toas a second end portion 23B. One end portion of the first transmissionline 21 is referred to as a third end portion 21A, and the other endportion thereof is referred to as a fourth end portion 21B. One endportion of the second transmission line 22 is referred to as a fifth endportion 22A, and the other end portion thereof is referred to as a sixthend portion 22B. The first end portion 23A of the third transmissionline 23 is connected to the third end portion 21A of the firsttransmission line 21, and the second end portion 23B is grounded. Here,“grounding” includes both DC grounding and AC grounding. The third endportion 21A of the first transmission line 21 is connected to a firstterminal 31 for connecting to an external circuit. The fourth endportion 21B of the first transmission line 21 is connected to the fifthend portion 22A of the second transmission line 22. The sixth endportion 22B of the second transmission line 22 is connected to a secondterminal 32 for connecting to an external circuit. That is, the firsttransmission line 21 and the second transmission line 22 are connectedin series to each other to form a transmission line, and both ends ofthe transmission line correspond to the first terminal 31 and the secondterminal 32.

The first transmission line 21 and the second transmission line 22 areeach electromagnetically coupled to the third transmission line 23. Inthe first embodiment, the coupling between the first transmission line21 and the third transmission line 23 corresponds to the couplingbetween coils having the same number of turns T, and also the couplingbetween the second transmission line 22 and the third transmission line23 corresponds to the coupling between coils having the same number ofturns T. For example, all of the first transmission line 21, the secondtransmission line 22, and the third transmission line 23 have the numberof turns T equal to n.

Next, the definition of the number of turns T in this specification willbe described with reference to FIGS. 2A and 2B.

FIG. 2A is a diagram illustrating an example of a coil pattern. An X-Yorthogonal coordinate system is defined in which an outer end portion ofthe coil pattern is an origin point O. This coil pattern has a pathextending from the origin point O to an end point E, which is an innerend portion of the coil pattern. The path length from the origin point Oto a point P on the coil pattern is represented by L. The Euclideandistance from the origin point O to the coordinates of the point P isrepresented by D.

FIG. 2B is a graph illustrating the relationship between the path lengthL and the Euclidean distance D at each point from the origin point O tothe end point E of the coil pattern. In the coil pattern illustrated inFIG. 2A, the Euclidean distance D has a first maximum value at a pointP1, has a minimum value at a point P2, and has a second maximum value ata point P3 before the end point E. The number of maximum values in thegraph illustrating the relationship between the path length L and theEuclidean distance D is defined as the number of turns T of the coilpattern. The number of turns T of the coil pattern illustrated in FIG.2A is 2.

The alternating currents flowing through the first transmission line 21,the second transmission line 22, and the third transmission line 23 willbe described. The current flowing from the first terminal 31 toward thesecond terminal 32 first flows through the first transmission line 21from the third end portion 21A toward the fourth end portion 21B, andthen flows through the second transmission line 22 from the fifth endportion 22A toward the sixth end portion 22B. The magnitude of thealternating current flowing through the first transmission line 21 isequal to the magnitude of the alternating current flowing through thesecond transmission line 22. The alternating current flowing through thefirst transmission line 21 induces an odd-mode current flowing throughthe third transmission line 23 from the first end portion 23A toward thesecond end portion 23B, and the alternating current flowing through thesecond transmission line 22 induces an odd-mode current flowing throughthe third transmission line 23 from the first end portion 23A toward thesecond end portion 23B. The direction in which the odd-mode currentinduced in the third transmission line 23 flows is opposite to thedirection in which the alternating current flows through the firsttransmission line 21 and the second transmission line 22. The odd-modecurrent induced by the current flowing through the first transmissionline 21 and the odd-mode current induced by the current flowing throughthe second transmission line 22 are equal to each other in terms of themagnitude and the direction.

The odd-mode current induced by the current flowing through the firsttransmission line 21 and the odd-mode current induced by the currentflowing through the second transmission line 22 flow through the thirdtransmission line 23 in a superimposed manner. Thus, the magnitude ofthe odd-mode current induced in the third transmission line 23 is twiceas much as the magnitude of the current flowing through a series circuitformed of the first transmission line 21 and the second transmissionline 22. When the magnitude of the current flowing from the firstterminal 31 into the transmission line transformer 20 is represented byi, the magnitude of the current flowing through the series circuitformed of the first transmission line 21 and the second transmissionline 22 is represented by (⅓)i, and the magnitude of the current flowingthrough the third transmission line 23 is represented by (⅔)i. Themagnitude of the current outputted from the second terminal 32 isrepresented by (⅓)i.

Next, voltages will be described. The voltage at the first terminal 31is represented by v1, and the voltage at the second terminal 32 isrepresented by v2. The voltage at the third end portion 21A of the firsttransmission line 21 and the voltage at the first end portion 23A of thethird transmission line 23 are equal to the voltage v1 at the firstterminal 31. The voltage at the sixth end portion 22B of the secondtransmission line 22 is equal to the voltage v2 at the second terminal32. The voltage at the fourth end portion 21B of the first transmissionline 21 is represented by v3. The voltage at the fifth end portion 22Aof the second transmission line 22 is equal to the voltage v3 at thefourth end portion 21B of the first transmission line 21. The voltage atthe second end portion 23B of the third transmission line 23 is 0 V.

The potential difference between the third end portion 21A and thefourth end portion 21B of the first transmission line 21 is equal to thepotential difference between the second end portion 23B and the firstend portion 23A of the third transmission line 23, and thus v1−v3=0−v1holds. Similarly, v3−v2=0−v1 holds between the second transmission line22 and the third transmission line 23. The solution of the simultaneousequations is 3×v1=v2. In other words, the voltage v2 at the secondterminal 32 is three times as much as the voltage v1 at the firstterminal 31.

When a load with an impedance R2 is connected to the second terminal 32,v2=(⅓)i×R2 holds. The impedance seen on the load side from the firstterminal 31 is represented by R1, and then v1=R1×i holds. The solutionof these equations is R1=( 1/9)R2. In other words, the impedance R1 seenon the load side from the first terminal 31 is 1/9 times as much as theimpedance R2 of the load connected to the second terminal 32. On theother hand, when a load is connected to the first terminal 31, theimpedance seen on the load side from the second terminal 32 is 9 timesas much as the impedance of the load connected to the first terminal 31.In this way, the transmission line transformer 20 according to the firstembodiment functions as an impedance transformation circuit having animpedance transformation ratio of about 9.

FIG. 1B is a schematic perspective view of the transmission linetransformer 20 according to the first embodiment, and FIG. 1C is across-sectional view taken along a dot-and-dash line 1C in FIG. 1B.

The first transmission line 21 and the second transmission line 22 aredisposed at different positions in the thickness direction of asubstrate 30 (FIG. 1C). The substrate 30 may be made of, for example, amagnetic insulating material or a dielectric material. Examples of asubstrate made of a dielectric material include a resin substrate and aceramic substrate. Alternatively, an insulating layer formed on asemiconductor substrate may be used as the substrate 30. The thirdtransmission line 23 is disposed between the first transmission line 21and the second transmission line 22. The first transmission line 21, thesecond transmission line 22, and the third transmission line 23 are eachconstituted by a substantially spiral conductor pattern whose dimensionis larger in the width direction than in the thickness direction. Inaddition, an extended line 24 and a ground conductor 35 (FIG. 1B) aredisposed in the substrate 30.

The third end portion 21A of the first transmission line 21, the firstend portion 23A of the third transmission line 23, and the sixth endportion 22B of the second transmission line 22 are disposed at positionsthat overlap each other in plan view. The fourth end portion 21B of thefirst transmission line 21 and the fifth end portion 22A of the secondtransmission line 22 are disposed at positions that overlap each otherin plan view. In the same layer as the third transmission line 23, aconductor pattern 29 is disposed at the position corresponding to thefourth end portion 21B of the first transmission line 21. A viaconductor 25 connects the third end portion 21A of the firsttransmission line 21 and the first end portion 23A of the thirdtransmission line 23. A via conductor 26 connects the fourth end portion21B of the first transmission line 21 and the conductor pattern 29, anda via conductor 27 connects the conductor pattern 29 and the fifth endportion 22A of the second transmission line 22. A via conductor 28connects the sixth end portion 22B of the second transmission line 22and the extended line 24. The third end portion 21A of the firsttransmission line 21 is connected to the first terminal 31, and theextended line 24 is connected to the second terminal 32. The second endportion 23B of the third transmission line 23 is connected to the groundconductor 35.

In plan view, the first transmission line 21 extends to turn in a firstturn direction (counterclockwise in FIG. 1B) from the third end portion21A. The third transmission line 23 extends to turn in a second turndirection (clockwise in FIG. 1B), which is opposite to the first turndirection, from the first end portion 23A. The second transmission line22 extends to turn in the first turn direction from the fifth endportion 22A.

In plan view, a substantially square-shaped closed virtual loop 36 isdefined. The third end portion 21A of the first transmission line 21,the first end portion 23A of the third transmission line 23, and thesixth end portion 22B of the second transmission line 22 are disposed atthe same position on the loop 36 in plan view. The fourth end portion21B of the first transmission line 21, the conductor pattern 29, and thefifth end portion 22A of the second transmission line 22 are disposed atthe same position inside the loop 36 in plan view. The third end portion21A, the first end portion 23A, and the sixth end portion 22B may bedisposed so as to partially overlap each other in plan view. Similarly,the fourth end portion 21B, the conductor pattern 29, and the fifth endportion 22A may be disposed so as to partially overlap each other inplan view.

The first transmission line 21 extends about one round along the loop 36in the first turn direction from the third end portion 21A, and extendsinward from the loop 36 to reach the fourth end portion 21B. The thirdtransmission line 23 extends about one round along the loop 36 in thesecond turn direction from the first end portion 23A, and extendsoutward from the loop 36 to reach the second end portion 23B. The secondtransmission line 22 extends from the fifth end portion 22A locatedinside the loop 36 toward the loop 36, and extends about one round alongthe loop 36 in the first turn direction to reach the sixth end portion22B. In this way, the first transmission line 21, the secondtransmission line 22, and the third transmission line 23 each constitutea coil pattern whose number of turns T is 1.

In the first transmission line 21, the second transmission line 22, andthe third transmission line 23, the portions along the loop 36 overlapeach other at least partially in plan view. Thus, the first transmissionline 21 is capacitively coupled to the third transmission line 23, andalso the second transmission line 22 is capacitively coupled to thethird transmission line 23.

Next, excellent effects of the first embodiment will be described.

A transmission line transformer having a two-layer structure formed ofthe first transmission line 21 and the third transmission line 23 has animpedance transformation ratio of about 4. In contrast, the transmissionline transformer 20 according to the first embodiment has an impedancetransformation ratio of about 9, which is larger than the impedancetransformation ratio of the transmission line transformer having atwo-layer structure. This is because the electromagnetic coupling of thethird transmission line 23 with both the first transmission line 21 andthe second transmission line 22 doubles the odd-mode current induced inthe third transmission line 23.

Furthermore, because the first transmission line 21, the secondtransmission line 22, and the third transmission line 23 are disposed soas to substantially overlap each other in plan view, an increase in theimpedance transformation ratio does not cause an increase in the areaoccupied by the transmission line transformer 20 in the substrate 30.Thus, the size of the transmission line transformer 20 can be reducedcompared to the configuration of achieving a large impedancetransformation ratio by cascade-connecting a plurality of transmissionline transformers each having a small impedance transformation ratio.

Next, a transmission line transformer according to a modificationexample of the first embodiment will be described.

In the first embodiment, the loop 36 (FIG. 1B) along which the firsttransmission line 21, the second transmission line 22, and the thirdtransmission line 23 extend is substantially square-shaped.Alternatively, the loop 36 may have another shape. For example, the loop36 may be substantially circular, elliptical, rectangular, polygonal, orthe like. In the first embodiment, the series circuit formed of thefirst transmission line 21 and the second transmission line 22 extendsto turn counterclockwise from the third end portion 21A, and the thirdtransmission line 23 extends to turn clockwise. Alternatively, theseturn directions may be reversed.

In the first embodiment, the first transmission line 21, the secondtransmission line 22, and the third transmission line 23 each extendabout one round along the loop 36. In each of the first transmissionline 21, the second transmission line 22, and the third transmissionline 23, the length of the portion along the loop 36 may be shorter thanthe length of the one round. Even with this structure, the number ofturns T can be 1 according to the definition of the number of turns T inthis specification (FIGS. 2A and 2B). To achieve sufficientelectromagnetic coupling, it is preferable that the number of turns T be1 or more in each of the first transmission line 21, the secondtransmission line 22, and the third transmission line 23.

In the first embodiment, the conductor patterns constituting the firsttransmission line 21, the second transmission line 22, and the thirdtransmission line 23 have widths that are substantially equal to eachother. Alternatively, the conductor pattern of the third transmissionline 23 may have a width larger than or equal to the width of each ofthe first transmission line 21 and the second transmission line 22. Inthis case, the conductor pattern of the first transmission line 21 andthe conductor pattern of the second transmission line 22 may preferablybe disposed inside the conductor pattern of the third transmission line23 in the width direction of the conductor patterns in plan view. Thisarrangement enables the capacitive coupling between the firsttransmission line 21 and the third transmission line 23 and thecapacitive coupling between the second transmission line 22 and thethird transmission line 23 to be increased. The increase in thecapacitive coupling makes it possible to reduce loss when inducing anodd-mode current in the third transmission line 23. As a result,insertion loss is reduced, and an impedance transformation ratio closerto a theoretical transformation ratio is obtained.

In the first embodiment, as illustrated in FIG. 1B, the extended line 24is disposed in a layer different from the layer of the secondtransmission line 22, and the second transmission line 22 and the secondterminal 32 are connected to each other with the extended line 24interposed therebetween. Alternatively, the extended line 24 and thesecond transmission line 22 may be disposed in the same layer. In thisconfiguration, the second transmission line 22 and the extended line 24are formed of a common conductor pattern, and thus the sixth end portion22B of the second transmission line 22 is not clearly specified. In thiscase, a portion at which the second transmission line 22 deviates fromthe loop 36 may be defined as the sixth end portion 22B.

In the first embodiment, as illustrated in FIG. 1B, the end of theportion extending outward from the portion along the loop 36 of thethird transmission line 23 is defined as the second end portion 23B.Alternatively, the end of the portion along the loop 36 may be definedas the second end portion 23B, and the portion extending from the secondend portion 23B to the ground conductor 35 may be regarded as a part ofthe extended line 24.

Similarly, the end of the portion along the loop 36 of the firsttransmission line 21 may be defined as the fourth end portion 21B, andthe portion extending inward from the loop 36 from the fourth endportion 21B may be regarded as a wiring line that connects the firsttransmission line 21 and the second transmission line 22. Similarly, theend of the portion along the loop 36 of the second transmission line 22may be defined as the fifth end portion 22A, and the portion extendinginward from the loop 36 from the fifth end portion 22A may be regardedas a wiring line that connects the first transmission line 21 and thesecond transmission line 22.

Second Embodiment

A transmission line transformer 20 according to a second embodiment willbe described with reference to FIGS. 3A and 3B. The same components asthose of the transmission line transformer 20 according to the firstembodiment will not be described.

FIG. 3A is a schematic diagram for describing the operation principle ofthe transmission line transformer 20 according to the second embodiment.In the first embodiment, the first transmission line 21, the secondtransmission line 22, and the third transmission line 23 have the samenumber of turns T. In the second embodiment, the number of turns T ofeach of the first transmission line 21 and the third transmission line23 is n, whereas the number of turns T of the second transmission line22 is 2n. That is, the number of turns T of the second transmission line22 is twice as many as the number of turns T of each of the firsttransmission line 21 and the third transmission line 23.

In this case, the magnitude of the odd-mode current induced in the thirdtransmission line 23 by the alternating current flowing through thesecond transmission line 22 is twice as much as the magnitude of thealternating current flowing through the second transmission line 22.Also, an odd-mode current is induced in the third transmission line 23by the alternating current flowing through the first transmission line21, as in the first embodiment. Thus, the magnitude of the odd-modecurrent induced in the third transmission line 23 is three times as muchas the magnitude of the alternating current flowing through the seriescircuit formed of the first transmission line 21 and the secondtransmission line 22. When the magnitude of the current flowing from thefirst terminal 31 into the transmission line transformer 20 isrepresented by i, the magnitude of the current flowing through theseries circuit formed of the first transmission line 21 and the secondtransmission line 22 is represented by (¼)i, and the magnitude of thecurrent flowing through the third transmission line 23 is represented by(¾)i. The magnitude of the current outputted from the second terminal 32is represented by (¼)i.

Regarding the voltages, v1−v3=0−v1 holds between the first transmissionline 21 and the third transmission line 23, as in the first embodiment.2(0−v1)=v3−v2 holds between the second transmission line 22 and thethird transmission line 23. The solution of the simultaneous equationsis v2=4×v1. That is, the voltage v2 at the second terminal 32 is fourtimes as much as the voltage v1 at the first terminal 31.

When a load is connected to the second terminal 32, the impedance seenon the load side from the first terminal 31 is 1/16 times as much as theimpedance of the load connected to the second terminal 32. On the otherhand, when a load is connected to the first terminal 31, the impedanceseen on the load side from the second terminal 32 is 16 times as much asthe impedance of the load connected to the first terminal 31. In thisway, the transmission line transformer 20 according to the secondembodiment functions as an impedance transformation circuit having animpedance transformation ratio of about 16.

FIG. 3B is a schematic perspective view of the transmission linetransformer 20 according to the second embodiment. In the firstembodiment, the second transmission line 22 (FIG. 1B) extends about oneround counterclockwise along the loop 36 from the fifth end portion 22A.In contrast, in the second embodiment, the second transmission line 22extends about two rounds counterclockwise along the loop 36 from thefifth end portion 22A. Thus, the number of turns T of the secondtransmission line 22 is twice as many as the number of turns T of thethird transmission line 23. When calculating the number of turns T ofthe second transmission line 22, the method described above withreference to FIGS. 2A and 2B is applied, with the sixth end portion 22B,which is the outer end portion, being the origin point. Because thenumber of turns T of the second transmission line 22 is 2, the width ofthe second transmission line 22 is smaller than the width of each of thefirst transmission line 21 and the third transmission line 23.

Next, excellent effects of the second embodiment will be described.

In the second embodiment, the number of turns T of the secondtransmission line 22 is twice as many as the number of turns T of thethird transmission line 23, and accordingly the impedance transformationratio is increased to about 16. Also in the second embodiment, the firsttransmission line 21, the second transmission line 22, and the thirdtransmission line 23 are disposed so as to overlap each other in planview, which makes it possible to suppress an increase in the areaoccupied by the transmission line transformer 20 in the substrate 30. Inthis way, an impedance transformation circuit with a large impedancetransformation ratio can be obtained while suppressing an increase inthe size of the circuit.

Next, a transmission line transformer 20 according to a modificationexample of the second embodiment will be described with reference toFIG. 4.

FIG. 4 is a schematic perspective view of the transmission linetransformer 20 according to this modification example of the secondembodiment. In this modification example, the second transmission line22 is constituted by a set of two coil patterns 221 and 222. The coilpatterns 221 and 222 each have the same shape as that of the secondtransmission line 22 according to the second embodiment (FIG. 3B) inplan view. The coil pattern 221 is disposed at the same position and inthe same posture as those of the second transmission line 22 of thetransmission line transformer 20 according to the second embodiment(FIG. 3B).

The coil pattern 222 is disposed across the coil pattern 221 from thethird transmission line 23 in the thickness direction such that the coilpattern 222 overlaps the coil pattern 221 in plan view.

A via conductor 225 connects a fifth end portion 221A of the coilpattern 221 and a fifth end portion 222A of the coil pattern 222. A viaconductor 226 connects a sixth end portion 221B of the coil pattern 221and a sixth end portion 222B of the coil pattern 222. As describedabove, the second transmission line 22 is constituted by the two coilpatterns 221 and 222 connected in parallel to each other.

In this modification example of the second embodiment, the parallelconnection between the two coil patterns 221 and 222 suppresses anincrease in the electrical resistance of the second transmission line22. As a result, the insertion loss of the transmission line transformer20 can be reduced.

Next, another modification example of the second embodiment will bedescribed.

In the second embodiment, the number of turns T of the secondtransmission line 22 is twice as many as the number of turns T of thethird transmission line 23, and accordingly the impedance transformationratio is increased to about 16. To achieve an impedance transformationratio of about 16 or more, the number of turns T of the secondtransmission line 22 may preferably be twice or more as many as thenumber of turns T of the third transmission line 23. Alternatively, thenumber of turns T of the first transmission line 21, instead of thesecond transmission line 22, may be twice or more as many as the numberof turns T of the third transmission line 23. In this way, the number ofturns T of at least one of the first transmission line 21 and the secondtransmission line 22 may preferably be twice or more as many as thenumber of turns T of the third transmission line 23.

Third Embodiment

A transmission line transformer 20 according to a third embodiment willbe described with reference to FIGS. 5A and 5B. The same components asthose of the transmission line transformer 20 according to the secondembodiment (FIGS. 3A and 3B) will not be described.

FIG. 5A is a schematic diagram for describing the operation principle ofthe transmission line transformer 20 according to the third embodiment.In the second embodiment, the first transmission line 21 and the thirdtransmission line 23 have the same number of turns T. In the thirdembodiment, the number of turns T of the first transmission line 21 is2n, whereas the number of turns T of the third transmission line 23 isn. That is, the number of turns T of the first transmission line 21 istwice as many as the number of turns T of the third transmission line23.

In this case, the magnitude of the odd-mode current induced in the thirdtransmission line 23 by the alternating current flowing through thefirst transmission line 21 is twice as much as the magnitude of thealternating current flowing through the first transmission line 21. Themagnitude of the odd-mode current induced in the third transmission line23 is four times as much as the magnitude of the alternating currentflowing through the series circuit formed of the first transmission line21 and the second transmission line 22. When the magnitude of thecurrent flowing from the first terminal 31 into the transmission linetransformer 20 is represented by i, the magnitude of the current flowingthrough the series circuit formed of the first transmission line 21 andthe second transmission line 22 is represented by (⅕)i, and themagnitude of the current flowing through the third transmission line 23is represented by (⅘)i. The magnitude of the current outputted from thesecond terminal 32 is represented by (⅕)i.

Regarding the voltages, 2(0−v1)=v1−v3 holds between the firsttransmission line 21 and the third transmission line 23. 2(0−v1)=v3−v2holds between the second transmission line 22 and the third transmissionline 23, as in the second embodiment. The solution of the simultaneousequations is v2=5×v1. That is, the voltage v2 at the second terminal 32is five times as much as the voltage v1 at the first terminal 31.

The impedance seen on the load side from the first terminal 31 is 1/25times as much as the impedance of the load connected to the secondterminal 32. On the other hand, when a load is connected to the firstterminal 31, the impedance seen on the load side from the secondterminal 32 is 25 times as much as the impedance of the load connectedto the first terminal 31. In this way, the transmission line transformer20 according to the third embodiment functions as an impedancetransformation circuit having an impedance transformation ratio of about25.

FIG. 5B is a schematic perspective view of the transmission linetransformer 20 according to the third embodiment. In the thirdembodiment, the first transmission line 21 extends about two roundsalong the loop 36 from the third end portion 21A and reaches the fourthend portion 21B in plan view. In the first transmission line 21, theportion of the second round is disposed inside the portion of the firstround. The first transmission line 21 has substantially the same widthas that of the third transmission line 23. The center line of theportion of the first round of the first transmission line 21 is locatedoutside the center line of the third transmission line 23, and thecenter line of the portion of the second round of the first transmissionline 21 is located inside the center line of the third transmission line23. With this arrangement, the first transmission line 21 hassubstantially the same width as that of the third transmission line 23,and has the number of turns T that is 2.

Next, excellent effects of the third embodiment will be described.

In the third embodiment, the number of turns T of not only the secondtransmission line 22 but also the first transmission line 21 is twice asmany as the number of turns T of the third transmission line 23, andaccordingly the impedance transformation ratio is increased to about 25.Also, in the third embodiment, the first transmission line 21, thesecond transmission line 22, and the third transmission line 23 aredisposed so as to overlap each other in plan view, which makes itpossible to suppress an increase in the area occupied by thetransmission line transformer 20 in the substrate 30. In this way, animpedance transformation circuit with a large impedance transformationratio can be obtained while suppressing an increase in the size of thecircuit.

In the third embodiment, the first transmission line 21 has a largerwidth than the second transmission line 22. Thus, the first transmissionline 21 has a smaller electrical resistance than the second transmissionline 22. The impedance at the fifth end portion 22A of the secondtransmission line 22 is transformed by the transmission line transformerconstituted by the first transmission line 21 and the third transmissionline 23 and becomes larger than the impedance at the third end portion21A of the first transmission line 21. Thus, actually, the magnitude(amplitude) of the current flowing through the series circuit formed ofthe first transmission line 21 and the second transmission line 22gradually decreases from the third end portion 21A of the firsttransmission line 21 toward the sixth end portion 22B of the secondtransmission line 22. That is, the magnitude (amplitude) of the currentflowing through the first transmission line 21 is larger than themagnitude (amplitude) of the current flowing through the secondtransmission line 22. By making the electrical resistance of the firsttransmission line 21, through which a relatively large current flows,lower than the electrical resistance of the second transmission line 22,through which a relatively small current flows, the loss resulting fromthe electrical resistance can be reduced.

Next, a transmission line transformer 20 according to a modificationexample of the third embodiment will be described with reference to FIG.6.

FIG. 6 is a schematic perspective view of the transmission linetransformer 20 according to this modification example of the thirdembodiment. In this modification example, the first transmission line 21is constituted by two coil patterns 211 and 212. The two coil patterns211 and 212 are disposed at different positions in the thicknessdirection of the substrate 30 (FIG. 1C). In plan view, the coil patterns211 and 212 each have the same shape as that of the first transmissionline 21 according to the third embodiment (FIG. 5B) and are eachdisposed in the same posture as that of the first transmission line 21according to the third embodiment.

The positional relationship between the coil pattern 212 and the thirdtransmission line 23 is the same as the positional relationship betweenthe first transmission line 21 and the third transmission line 23according to the third embodiment (FIG. 5B). The coil pattern 211 isdisposed across the coil pattern 212 from the third transmission line23.

A via conductor 215 connects a third end portion 211A of the coilpattern 211 and a third end portion 212A of the coil pattern 212. A viaconductor 216 connects a fourth end portion 211B of the coil pattern 211and a fourth end portion 212B of the coil pattern 212. As describedabove, the first transmission line 21 is constituted by the two coilpatterns 211 and 212 connected in parallel to each other.

The second transmission line 22 is constituted by the two coil patterns221 and 222, like the second transmission line 22 of the transmissionline transformer 20 according to the modification example of the secondembodiment illustrated in FIG. 4.

Next, excellent effects of this modification example of the thirdembodiment will be described.

In this modification example of the third embodiment, the firsttransmission line 21 is constituted by the two coil patterns 211 and 212connected in parallel to each other, and also the second transmissionline 22 is constituted by the two coil patterns 221 and 222 connected inparallel to each other. Thus, the electrical resistances of the firsttransmission line 21 and the second transmission line 22 are decreased.As a result, the insertion loss of the transmission line transformer 20can be reduced.

In this modification example, the two coil patterns 211 and 212constituting the first transmission line 21 have a larger width than thetwo coil patterns 221 and 222 constituting the second transmission line22. Thus, as in the third embodiment, the electrical resistance of thefirst transmission line 21, through which a relatively large currentflows, is lower than the electrical resistance of the secondtransmission line 22, through which a relatively small current flows. Asa result, the loss resulting from the electrical resistance can bereduced.

Next, another modification example of the third embodiment will bedescribed.

In the third embodiment, the number of turns T of each of the firsttransmission line 21 and the second transmission line 22 is twice asmany as the number of turns T of the third transmission line 23.Alternatively, the ratio of the number of turns T may be other than 2.By setting the number of turns T of each of the first transmission line21 and the second transmission line 22 to be larger than or equal to thenumber of turns T of the third transmission line 23, an impedancetransformation ratio of about 9 or more can be achieved.

Fourth Embodiment

An amplifying circuit according to a fourth embodiment will be describedwith reference to FIG. 7.

FIG. 7 is an equivalent circuit diagram of the amplifying circuitaccording to the fourth embodiment. The first terminal 31 of thetransmission line transformer 20 is connected to an output terminal ofan amplifying element 40 that amplifies a high-frequency signal, with aDC-cut capacitor 44 interposed therebetween. For example, aheterojunction bipolar transistor may be used as the amplifying element40. The transmission line transformer 20 used here is the transmissionline transformer 20 according to any one of the first to thirdembodiments and their modification examples. The high-frequency signalamplified by the amplifying element 40 is inputted to the transmissionline transformer 20 through the DC-cut capacitor 44. The second terminal32 of the transmission line transformer 20 is connected to a DC-cutcapacitor 45, and the signal outputted from the second terminal 32 issupplied to a load through the DC-cut capacitor 45.

The output terminal of the amplifying element 40 is grounded through aharmonic termination circuit 41. The output terminal of the amplifyingelement 40 is also connected to a power supply circuit 46 with aninductor 42 interposed therebetween. DC power is supplied from the powersupply circuit 46 to the amplifying element 40 through the inductor 42.The wiring line connecting the power supply circuit 46 and the inductor42 is grounded through a decoupling capacitor 43.

Next, excellent effects of the fourth embodiment will be described.

In the fourth embodiment, the transmission line transformer 20 functionsas an impedance matching circuit between the amplifying element 40 andthe load. In the fourth embodiment, the impedance seen on thetransmission line transformer 20 side from the output terminal of theamplifying element 40 is lower than the impedance seen on the load sidefrom the second terminal 32. In the fourth embodiment, the transmissionline transformer 20 according to any one of the first to thirdembodiments and their modification examples is used as the transmissionline transformer 20. Thus, an impedance transformation ratio larger thanthat of a transmission line transformer according to the related art canbe achieved, and the size of the impedance matching circuit can bereduced.

Fifth Embodiment

An amplifying circuit according a fifth embodiment will be describedwith reference to FIG. 8. The same components as those of the amplifyingcircuit according to the fourth embodiment (FIG. 7) will not bedescribed.

FIG. 8 is an equivalent circuit diagram of the amplifying circuitaccording to the fifth embodiment. In the fourth embodiment, the outputterminal of the amplifying element 40 is connected to the first terminal31 of the transmission line transformer 20 with the DC cut capacitor 44(FIG. 7) interposed therebetween. In the fifth embodiment, the outputterminal of the amplifying element 40 is directly connected to the firstterminal 31 of the transmission line transformer 20. In the fourthembodiment, the output terminal of the amplifying element 40 isconnected to the power supply circuit 46 with the inductor 42 (FIG. 7)interposed therebetween. In the fifth embodiment, the second end portion23B of the third transmission line 23 of the transmission linetransformer 20 is connected to the power supply circuit 46 with theinductor 42 interposed therebetween. DC power is supplied from the powersupply circuit 46 to the amplifying element 40 through the inductor 42and the third transmission line 23.

The power supply circuit 46 can be regarded as the ground in term of AC.Thus, the second end portion 23B of the third transmission line 23 isAC-grounded through the inductor 42. The third transmission line 23 alsoserves as a path for supplying DC power.

Next, excellent effects of the fifth embodiment will be described.

In the fifth embodiment, as in the fourth embodiment, an impedancetransformation ratio larger than that of a transmission line transformeraccording to the related art can be achieved, and the size of theimpedance matching circuit can be reduced. In the fifth embodiment, theDC-cut capacitor 44 according to the fourth embodiment (FIG. 7) is notnecessary.

A modification example of the fifth embodiment will be described. In thefifth embodiment, the second end portion 23B of the third transmissionline 23 is connected to the power supply circuit 46 with the inductor 42interposed therebetween. When the third transmission line 23 has asufficient inductance, the inductor 42 is not necessary, and the secondend portion 23B of the third transmission line 23 may be directlyconnected to the power supply circuit 46.

Sixth Embodiment

An amplifying circuit according to a sixth embodiment will be describedwith reference to FIG. 9. In the fourth embodiment (FIG. 7) and thefifth embodiment (FIG. 8), the transmission line transformer 20 isconnected to the output terminal of the amplifying element 40. In thesixth embodiment, the transmission line transformer 20 is connected toan input terminal of the amplifying element 40. The transmission linetransformer 20 used here is the transmission line transformer 20according to any one of the first to third embodiments and theirmodification examples.

FIG. 9 is an equivalent circuit diagram of the amplifying circuitaccording to the sixth embodiment. A high-frequency signal is inputtedfrom a high-frequency signal input terminal 50 to the second terminal 32of the transmission line transformer 20 through a DC-cut capacitor 47.The first terminal 31 of the transmission line transformer 20 isconnected to the input terminal of the amplifying element 40 with aDC-cut capacitor 48 interposed therebetween. The transmission linetransformer 20 functions as an impedance matching circuit on the inputside of the amplifying element 40. In the sixth embodiment, theimpedance seen on the transmission line transformer 20 side from thehigh-frequency signal input terminal 50 is higher than the impedanceseen on the amplifying element 40 side from the first terminal 31. Inthis way, impedance transformation for decreasing the impedance isperformed in the sixth embodiment.

Next, excellent effects of the sixth embodiment will be described.

In the sixth embodiment, as in the fourth and fifth embodiments, animpedance transformation ratio larger than that of a transmission linetransformer according to the related art can be achieved, and the sizeof the impedance matching circuit can be reduced.

Seventh Embodiment

An amplifying circuit according to a seventh embodiment will bedescribed with reference to FIG. 10. In the seventh embodiment,amplifying elements 40 are connected in multiple stages to form amulti-stage power amplifying circuit.

FIG. 10 is a block diagram of the amplifying circuit according to theseventh embodiment. A plurality of amplifying elements 40 are connectedin multiple stages between the high-frequency signal input terminal 50and a high-frequency signal output terminal 51 from which an amplifiedhigh-frequency signal is outputted. An input-side transmission linetransformer 20 is disposed between the high-frequency signal inputterminal 50 and a first-stage amplifying element 40. An output-sidetransmission line transformer 20 is disposed between a last-stageamplifying element 40 and the high-frequency signal output terminal 51.An interstage transmission line transformer 20 is disposed between oneamplifying element 40 and the subsequent amplifying element 40. As eachof the input-side transmission line transformer 20, the output-sidetransmission line transformer 20, and the interstage transmission linetransformer 20, the transmission line transformer 20 according to anyone of the first to third embodiments and their modification examples isused.

DC power is supplied to the plurality of amplifying elements 40 from thepower supply circuit 46 through the inductors 42. DC bias is supplied tothe plurality of amplifying elements 40 from bias control circuits 53.

Next, excellent effects of the seventh embodiment will be described.

In the seventh embodiment, the transmission line transformers 20function as input-side, interstage, and output-side impedance matchingcircuits. In the seventh embodiment, the sizes of the impedance matchingcircuits can be reduced as in the fourth embodiment (FIG. 7), the fifthembodiment (FIG. 8), and the sixth embodiment (FIG. 9).

A modification example of the seventh embodiment will be described.

In the seventh embodiment, the transmission line transformer 20according to any one of the first to third embodiments and theirmodification examples is used as each of the input-side, output-side,and interstage impedance matching circuits. At a part where a largeimpedance transformation ratio is not necessary, the transmission linetransformer 20 according to any one of the first to third embodimentsand their modification examples is not necessary. For example, atransmission line transformer that does not include the secondtransmission line 22 in FIG. 1A but includes the first transmission line21 and the third transmission line 23 in FIG. 1A may be used as animpedance matching circuit. Alternatively, a ladder impedance matchingcircuit formed of a capacitance and an inductance may be used. Forexample, the transmission line transformer 20 according to any one ofthe first to third embodiments and their modification examples may beused as at least one of the input-side, output-side, and interstageimpedance matching circuits.

Eighth Embodiment

Simulation results of input/output impedances of impedancetransformation circuits according to an eighth embodiment will bedescribed with reference to FIGS. 11A to 13B.

FIGS. 11A and 11B are block diagrams of the impedance transformationcircuits according to the eighth embodiment as simulation targets. Asthe impedance transformation circuits, the transmission line transformer20 according to the second embodiment (FIGS. 3A and 3B) having animpedance transformation ratio of about 16 is used.

In the impedance transformation circuit illustrated in FIG. 11A, an ACpower supply 55 having an output impedance of about 3Ω is connected tothe first terminal 31 of the transmission line transformer 20, and thesecond terminal 32 is terminated with about 50Ω. In the impedancetransformation circuit illustrated in FIG. 11B, the AC power supply 55having an output impedance of about 50Ω is connected to the secondterminal 32 of the transmission line transformer 20, and the firstterminal 31 was terminated with about 3Ω.

In the impedance transformation circuit illustrated in FIG. 11A, theimpedance seen on the transmission line transformer 20 side from thefirst terminal 31 is represented by Z1. In the impedance transformationcircuit illustrated in FIG. 11B, the impedance seen on the transmissionline transformer 20 side from the second terminal 32 is represented byZ2. An electromagnetic-field simulation is performed with the frequencybeing changed from about 100 MHz to about 20 GHz, thereby obtaining theimpedances Z1 and Z2. The transmission line transformer 20 is designedto achieve an impedance transformation ratio of about 16 in thefrequency band ranging from about 2.3 GHz to about 2.69 GHz.

FIG. 12A is a graph obtained by plotting the trajectory of the impedanceZ1 at various frequencies on a Smith chart. A reference impedance Zrefat the reference point (center point) of the Smith chart is about 3Ω.The impedance Z1 in the frequency band ranging from about 2.3 GHz toabout 2.69 GHz, the impedance Z1 in the frequency band of the secondharmonic (ranging from about 4.6 GHz to about 5.38 GHz), and theimpedance Z1 in the frequency band of the third harmonic (ranging fromabout 6.9 GHz to about 8.07 GHz) are represented by the bold lines. Itcan be seen that the impedance Z1 is near the reference point of theSmith chart and is approximately 3Ω in the frequency band ranging fromabout 2.3 GHz to about 2.69 GHz. As a result, it is confirmed that theimpedance is transformed from about 50Ω to about 1/16, that is, about3Ω.

FIG. 12B is a graph obtained by plotting the trajectory of the impedanceZ2 at various frequencies on a Smith chart. A reference impedance Zrefat the reference point (center point) of the Smith chart is about 50Ω.The impedance Z2 in the frequency band ranging from about 2.3 GHz toabout 2.69 GHz, the impedance Z2 in the frequency band of the secondharmonic (ranging from about 4.6 GHz to about 5.38 GHz), and theimpedance Z2 in the frequency band of the third harmonic (ranging fromabout 6.9 GHz to about 8.07 GHz) are represented by bold lines. It canbe seen that the impedance Z2 is near the reference point of the Smithchart and is approximately 50Ω in the frequency band ranging from about2.3 GHz to about 2.69 GHz. As a result, it is confirmed that theimpedance is transformed from about 3Ω to about 16 times, that is, about50Ω.

FIGS. 13A and 13B are graphs illustrating simulation results ofinsertion loss of the transmission line transformer 20. The horizontalaxis represents frequency in “GHz”, and the vertical axis representsinsertion loss in “dB”. An insertion loss IL is defined by the followingequation.

${IL} = {10\log\frac{{S_{21}}^{2}}{1 - {S_{11}}^{2}}}$Here, S₁₁ and S₂₁ are scattering parameters. A smaller absolute value onthe vertical axis represents a smaller loss. FIG. 13B is an enlargedview of the range of frequencies 1 GHz to 6 GHz on the horizontal axisof FIG. 13A. It can be seen that the insertion loss is small in thefrequency band ranging from about 2.3 GHz to about 2.69 GHz.

From the simulations in the eighth embodiment, it is confirmed that animpedance matching circuit having an impedance transformation ratio ofabout 16 can be obtained by using the transmission line transformer 20according to the second embodiment. Also, it is confirmed that animpedance matching circuit with low insertion loss can be obtained byusing the transmission line transformer 20 according to the secondembodiment. These simulation results also show that an impedancematching circuit with low insertion loss can be obtained by using thetransmission line transformer 20 according to the first embodiment orthe third embodiment.

Ninth Embodiment

Simulation results of input/output impedances of impedancetransformation circuits according to a ninth embodiment will bedescribed with reference to FIGS. 14A to 16B.

FIGS. 14A and 14B are block diagrams of the impedance transformationcircuits as simulation targets. The impedance transformation circuitillustrated in FIG. 14A is formed by connecting the harmonic terminationcircuit 41 between the AC power supply 55 and the transmission linetransformer 20 illustrated in FIG. 11A. The impedance transformationcircuit illustrated in FIG. 14B is formed by connecting the harmonictermination circuit 41 between the load and the transmission linetransformer 20 illustrated in FIG. 11B.

In FIG. 14A, the impedance seen on the harmonic termination circuit 41and the transmission line transformer 20 side from the AC power supply55 is represented by Z1. In FIG. 14B, the impedance seen on the harmonictermination circuit 41 and the transmission line transformer 20 sidefrom the AC power supply 55 is represented by Z2. Anelectromagnetic-field simulation is performed with the frequency beingchanged from about 100 MHz to about 20 GHz, thereby obtaining theimpedances Z1 and Z2.

FIG. 15A is a graph obtained by plotting the trajectory of the impedanceZ1 at various frequencies on a Smith chart. A reference impedance Zrefat the reference point (center point) of the Smith chart is about 3Ω.The impedance Z1 in the frequency band ranging from about 2.3 GHz toabout 2.69 GHz, the impedance Z1 in the frequency band of the secondharmonic (ranging from about 4.6 GHz to about 5.38 GHz), and theimpedance Z1 in the frequency band of the third harmonic (ranging fromabout 6.9 GHz to about 8.07 GHz) are represented by bold lines. As inthe eighth embodiment (FIG. 12A), it can be seen that the impedance Z1is near the reference point of the Smith chart and is approximately 3Ωin the frequency band ranging from about 2.3 GHz to about 2.69 GHz. As aresult, it is confirmed that the impedance is transformed from about 50Ωto about 1/16, that is, about 3Ω.

FIG. 15B is a graph obtained by plotting the trajectory of the impedanceZ2 at various frequencies on a Smith chart. A reference impedance Zrefat the reference point (center point) of the Smith chart is about 50Ω.The impedance Z2 in the frequency band ranging from about 2.3 GHz toabout 2.69 GHz, the impedance Z2 in the frequency band of the secondharmonic (ranging from about 4.6 GHz to about 5.38 GHz), and theimpedance Z2 in the frequency band of the third harmonic (ranging fromabout 6.9 GHz to about 8.07 GHz) are represented by bold lines. It canbe seen that the impedance Z2 is near the reference point of the Smithchart and is approximately 50Ω in the frequency band ranging from about2.3 GHz to about 2.69 GHz. As a result, it is confirmed that theimpedance is transformed from about 3Ω to about 16 times, that is, about50Ω.

FIGS. 16A and 16B are graphs illustrating simulation results ofinsertion loss of the transmission line transformer 20. The horizontalaxis represents frequency in “GHz”, and the vertical axis representsinsertion loss in “dB”. A smaller absolute value on the vertical axisrepresents a smaller loss. FIG. 16B is an enlarged view of the range offrequencies 1 GHz to 6 GHz on the horizontal axis of FIG. 16A. It can beseen that the insertion loss is small in the frequency band ranging fromabout 2.3 GHz to about 2.69 GHz.

From the simulations in the ninth embodiment, it is confirmed that animpedance matching circuit with low insertion loss can be obtained byusing the transmission line transformer 20 according to the secondembodiment, also in the configuration including the harmonic terminationcircuit 41. The comparison between FIG. 12A and FIG. 15A shows that theharmonic termination circuit 41 causes a decrease in the impedance Z1for the second harmonic and the third harmonic. Thus, the transmissionline transformer 20 according to the second embodiment, which is asimulation target, can be used also as an output matching circuit forrealizing the operation of a switching mode power amplifier.Accordingly, the power-added efficiency of the switching mode poweramplifier is improved.

In addition, it can be easily understood, from these simulation results,that an impedance matching circuit with low insertion loss can beobtained by using the transmission line transformer 20 according to thefirst embodiment or the third embodiment.

Tenth Embodiment

An amplifying circuit according to a tenth embodiment will be describedwith reference to FIGS. 17, 18, and 19. The same components as those ofthe amplifying circuit according to the fourth embodiment (FIG. 7) willnot be described.

FIG. 17 is an equivalent circuit diagram of the amplifying circuitaccording to the tenth embodiment. The amplifying circuit according tothe tenth embodiment includes two amplifying systems 60A and 60B. Thetwo amplifying systems 60A and 60B each include the amplifying element40 and the transmission line transformer 20. In each of the twoamplifying systems 60A and 60B, the configuration from the amplifyingelement 40 to the second terminal 32 is the same as the configurationfrom the amplifying element 40 to the second terminal 32 of theamplifying circuit according to the fourth embodiment (FIG. 7). Thesecond terminals 32 of the two amplifying systems 60A and 60B areconnected to each other and are connected to one electrode of the singleDC-cut capacitor 45. The other electrode of the DC-cut capacitor 45 isconnected to an output terminal 37. A resistance element 61 and acapacitor 62 are connected in parallel to each other between the outputterminal of the amplifying element 40 of the amplifying system 60A andthe output terminal of the amplifying element 40 of the amplifyingsystem 60B. A connection circuit formed of the resistance element 61 andthe capacitor 62 is referred to as an inter-system phase-shift circuit65.

The operation of the amplifying circuit according to the tenthembodiment will be described. The amplifying circuit according to thetenth embodiment constitutes a Webb's power combiner.

High-frequency signals having substantially the same phase andsubstantially the same amplitude are inputted to the two amplifyingelements 40. The two amplifying elements 40 amplify the inputhigh-frequency signals and output high-frequency signals havingsubstantially the same phase and substantially the same amplitude. Thehigh-frequency signals amplified by the two amplifying elements 40 aresubjected to impedance transformation performed by the two transmissionline transformers 20 and are then outputted from the second terminals32. The high-frequency signals outputted from the second terminals 32are combined before the DC-cut capacitor 45 and the resulting signal isoutputted from the output terminal 37.

The function of the inter-system phase-shift circuit 65 that connectsthe two amplifying systems 60A and 60B will be described. A current pathextending from the output terminal of the amplifying element 40 of theamplifying system 60A to the output terminal of the amplifying element40 of the amplifying system 60B includes a first signal path 63 passingthrough the transmission line transformers 20 and a second signal path64 passing through the inter-system phase-shift circuit 65. The firstsignal path 63 and the second signal path 64 are configured such thatthe difference between the amount of phase change in the high-frequencysignal transmitted through the first signal path 63 and the amount ofphase change in the high-frequency signal transmitted through the secondsignal path 64 from the output terminal of the amplifying element 40 ofthe amplifying system 60A to the output terminal of the amplifyingelement 40 of the amplifying system 60B is about 180 degrees. Forexample, the amount of phase change in the case of passing through thefirst signal path 63 is about +90 degrees, whereas the amount of phasechange in the case of passing through the second signal path 64 is about−90 degrees.

The two high-frequency signals that are outputted from the amplifyingelement 40 of the amplifying system 60B, that are transmitted throughthe first signal path 63 and the second signal path 64, and that reachthe output terminal of the amplifying element 40 of the amplifyingsystem 60B have a phase difference of about 180 degrees, and thus poweroffset occurs. That is, the high-frequency signal outputted from theamplifying element 40 of the amplifying system 60A hardly appears at theoutput terminal of the amplifying element 40 of the amplifying system60B. Similarly, the high-frequency signal outputted from the amplifyingelement 40 of the amplifying system 60B hardly appears at the outputterminal of the amplifying element 40 of the amplifying system 60A.Thus, high-frequency isolation is secured between the output terminalsof the two amplifying elements 40 of the two amplifying systems 60A and60B. As a result, almost all the power of the high-frequency signalsoutputted from the two amplifying elements 40 can be transmitted to theoutput terminal 37.

FIG. 18 is a plan view illustrating a plurality of conductor patternsdisposed in a first conductor layer of the amplifying circuit accordingto the tenth embodiment. In FIG. 18, the conductor patterns are hatched.The conductor patterns in the first layer include the first transmissionlines 21 and parts of the inductors 42 of the two amplifying systems 60Aand 60B, and lands 81, 82, 85, and 86 for mounting surface mountdevices. Each first transmission line 21 is constituted by a conductorpattern whose number of turns T is 1. Furthermore, lands 83 and 84common to the two amplifying systems 60A and 60B are disposed in thefirst conductor layer.

The conductor patterns constituting the parts of the two inductors 42are connected to the respective lands 81. The output terminals of theamplifying elements 40 and one terminals of the DC-cut capacitors 44 areconnected to the lands 81. Furthermore, the resistance element 61 andthe capacitor 62 are connected between the two lands 81. One endportions of the conductor patterns of the first transmission lines 21are connected to the lands 82. The other terminals of the DC-cutcapacitors 44 are connected to the lands 82. The decoupling capacitors43 are connected between the lands 85 and the lands 86.

The plurality of conductor patterns constituting the amplifying system60A and the plurality of conductor patterns constituting the amplifyingsystem 60B are axisymmetric in plan view. A grounded conductor pattern71 is disposed along the symmetry axis between the plurality ofconductor patterns constituting the amplifying system 60A and theplurality of conductor patterns constituting the amplifying system 60B.Furthermore, the land 83 and the land 84 are disposed on the symmetryaxis. The DC-cut capacitor 45 is connected between the land 83 and theland 84.

FIG. 19 is an exploded perspective view of a plurality of conductorlayers provided in the substrate 30 used for the amplifying circuitaccording to the tenth embodiment. Conductor layers 91 to 98 as first toeighth layers are disposed in order in the thickness direction from amount surface on which circuit components are mounted. In FIG. 19, theconductor patterns in the odd-numbered conductor layers 91, 93, 95, and97 are given hatching with a relatively high density, and the conductorpatterns in the even-numbered conductor layers 92, 94, 96, and 98 aregiven hatching with a relatively low density.

The plurality of conductor patterns disposed in the conductor layer 91as the first layer are as illustrated in FIG. 18. In FIG. 19, a symbolformed of a solid circle and line segments extending upward and downwardis given at the position where via conductors connected to both aconductor pattern in an upper layer and a conductor pattern in a lowerlayer are connected. A symbol formed of a solid circle and a linesegment extending downward is given at the position where only a viaconductor connected to a conductor pattern in a lower layer isconnected. A symbol formed of a hollow circle and a line segmentextending upward is given at the position where only a via conductorconnected to a conductor pattern in an upper layer is connected.

The grounded conductor pattern 71 is disposed in each of the conductorlayers 92 to 97 as the second to seventh layers. The grounded conductorpatterns 71 in the individual conductor layers substantially overlapeach other in plan view. The grounded conductor patterns 71 adjacent toeach other in the vertical direction are connected to each other by fourvia conductors.

In the conductor layer 98 as the eighth layer, a ground plane 70 and apower supply wiring line 72 are disposed. The grounded conductor pattern71 in the seventh layer is connected to the ground plane 70 by the fourvia conductors. In this way, all the grounded conductor patterns 71 inthe first to seventh layers are grounded. The power supply wiring line72 is connected to the power supply circuit 46 (FIG. 17).

The plurality of conductor patterns constituting the two inductors 42are disposed in the conductor layers 91 to 94 as the first to fourthlayers such that two conductor patterns are disposed in each layer. Thenumber of turns T of each conductor pattern in each conductor layeris 1. In each inductor 42, the termination portion of the conductorpattern in the fourth layer constituting the inductor 42 is connected tothe land 86 in the first layer, with a plurality of via conductors andthe conductor patterns in the third and second layers interposedtherebetween. Furthermore, in each inductor 42, the termination portionof the conductor pattern in the fourth layer constituting the inductor42 is connected to a power supply wiring line 76 in the seventh layer,with the conductor patterns in the fifth and sixth layers and aplurality of via conductors interposed therebetween. The power supplywiring line 76 in the seventh layer is connected to the power supplywiring line 72 in the eighth layer with a plurality of via conductorsinterposed therebetween.

The lands 85 in the first layer are connected to the ground plane 70,with a plurality of via conductors and the conductor patterns in thesecond to seventh layers interposed therebetween.

The two third transmission lines 23 are disposed in the conductor layer92 as the second layer. Each of the third transmission lines 23 isconstituted by a conductor pattern whose number of turns T is 1. In eachthird transmission line 23, one end portion is connected to the groundedconductor pattern 71 in the same conductor layer, whereas the other endportion is connected to the land 82-side end portion of the firsttransmission line 21, with a via conductor interposed therebetween.

The two second transmission lines 22 are disposed in the conductor layer93 as the third layer. Each of the second transmission lines 22 isconstituted by a substantially spiral conductor pattern whose number ofturns T is 2. In each second transmission line 22, the inner end portionis connected to one end portion of the first transmission line 21, witha plurality of via conductors and the conductor pattern in the secondlayer interposed therebetween. In each second transmission line 22, theouter end portion is connected to a conductor pattern 75 in the fourthlayer, with a via conductor interposed therebetween. The conductorpattern 75 is connected to the land 83 in the first layer, with aplurality of via conductors and the conductor patterns in the second andthird layers interposed therebetween.

In each of the conductor layers 92 to 96 as the second to sixth layers,the conductor patterns belonging to the amplifying system 60A and theconductor patterns belonging to the amplifying system 60B areaxisymmetric, like the conductor patterns in the conductor layer 91 asthe first layer.

Next, excellent effects of the tenth embodiment will be described.

In the tenth embodiment, the powers of high-frequency signals outputtedfrom the two amplifying elements 40 are combined, thereby obtainingoutput power that is about twice (i.e., +3 dB) as much as the power inthe case of using a single amplifying element 40. Furthermore, as in thefirst embodiment, the size of the amplifying circuit can be reducedcompared to the configuration of achieving a large impedancetransformation ratio by cascade-connecting a plurality of transmissionline transformers each having a small impedance transformation ratio. Inaddition, the number of components can be reduced compared to the casewhere the impedance transformation circuit is constituted by a pluralityof surface mount devices including a capacitor and an inductor.Furthermore, the degradation in characteristics of the amplifyingcircuit resulting from the variations in characteristics of individualsurface mount devices can be suppressed.

The conductor patterns of the amplifying system 60A and the conductorpatterns of the amplifying system 60B are axisymmetric, and thus a phaseshift of high-frequency signals at the second terminals 32 (FIG. 17)serving as power combining terminals can be suppressed, and the accuracyof phase matching can be increased.

Furthermore, the grounded conductor pattern 71 is disposed between theconductor patterns of the amplifying system 60A and the conductorpatterns of the amplifying system 60B. Thus, the leakage of the powerfrom one of the amplifying systems 60A and 60B to the other can bereduced. As a result, the loss caused by leakage of power can bereduced.

Eleventh Embodiment

An amplifying circuit according to an eleventh embodiment will bedescribed with reference to FIG. 20. The same components as those of theamplifying circuit according to the tenth embodiment (FIGS. 17, 18, and19) will not be described.

FIG. 20 is an equivalent circuit diagram of the amplifying circuitaccording to the eleventh embodiment. In the tenth embodiment, theconfiguration from the amplifying element 40 to the second terminal 32in each of the two amplifying systems 60A and 60B (FIG. 17) is the sameas the configuration from the amplifying element 40 to the secondterminal 32 of the amplifying circuit according to the fourth embodiment(FIG. 7). In contrast, in the eleventh embodiment, the configurationfrom the amplifying element 40 to the second terminal 32 in each of thetwo amplifying systems 60A and 60B is the same as the configuration fromthe amplifying element 40 to the second terminal 32 of the amplifyingcircuit according to the fifth embodiment (FIG. 8).

Next, excellent effects of the eleventh embodiment will be described.

In the eleventh embodiment, as in the tenth embodiment, output powerabout twice as much as the power in the case of using a singleamplifying element 40 can be obtained. Furthermore, the degradation incharacteristics of the amplifying circuit resulting from the variationsin characteristics of individual surface mount devices can besuppressed. Furthermore, as in the fifth embodiment, the DC-cutcapacitors 44 according to the tenth embodiment (FIG. 17) are notnecessary.

Twelfth Embodiment

A transmission line transformer according to a twelfth embodiment willbe described with reference to FIGS. 21 to 24. The transmission linetransformer according to the first embodiment (FIG. 1A) is applied to asingle-end transmission line, whereas the transmission line transformeraccording to the twelfth embodiment is applied to differentialtransmission lines.

FIG. 21 is a schematic diagram for describing the operation principle ofthe transmission line transformer according to the twelfth embodiment.The transmission line transformer according to the twelfth embodimentincludes a first transmission line group 100P and a second transmissionline group 100N. The first transmission line group 100P and the secondtransmission line group 100N each include a main line 101 and a sub line102. The main line 101 includes a first line 101A and a second line 101Bconnected in series to each other. A point at which the first line 101Aand the second line 101B are connected to each other is referred to as amutual connection point PI.

In each of the first transmission line group 100P and the secondtransmission line group 100N, the first line 101A, the second line 101B,and the sub line 102 extend in parallel to each other. The first line101A and the second line 101B of the first transmission line group 100Pare each electromagnetically coupled to the sub line 102 of the firsttransmission line group 100P. The coupling between the first line 101Aand the sub line 102 and the coupling between the second line 101B andthe sub line 102 each correspond to the coupling between coils havingthe same number of turns. Similarly, the first line 101A and the secondline 101B of the second transmission line group 100N are eachelectromagnetically coupled to the sub line 102 of the secondtransmission line group 100N.

The main line 101 of the first transmission line group 100P includes afirst end portion E1 and a second end portion E2 that are connected to afirst differential signal port 110P and a second differential signalport 111P, respectively. The main line 101 of the second transmissionline group 100N includes a first end portion E1 and a second end portionE2 that are connected to a first differential signal port 110N and asecond differential signal port 111N, respectively. The line between thefirst end portion E1 and the mutual connection point PI corresponds tothe first line 101A, and the line between the mutual connection point PIand the second end portion E2 corresponds to the second line 101B. Themain line 101 of the first transmission line group 100P and the mainline 101 of the second transmission line group 100N function asdifferential transmission lines.

Of both end portions of the sub line 102, the end portion correspondingto the first end portion E1 of the first line 101A in the lengthdirection of the lines is defined as a first end portion E1, and the endportion corresponding to the mutual connection point PI of the firstline 101A is defined as a second end portion E2. The second line 101Band the sub line 102 are coupled to each other such that the first endportion E1 and the second end portion E2 of the sub line 102 correspondto the mutual connection point PI and the second end portion E2 of thesecond line 101B, respectively, in the length direction of the lines.

The first end portion E1 of the sub line 102 of the first transmissionline group 100P is connected to the first end portion E1 of the mainline 101 of the second transmission line group 100N. The first endportion E1 of the sub line 102 of the second transmission line group100N is connected to the first end portion E1 of the main line 101 ofthe first transmission line group 100P. The second end portion E2 of thesub line 102 of the first transmission line group 100P is connected tothe second end portion E2 of the sub line 102 of the second transmissionline group 100N.

Next, the operation principle of the transmission line transformeraccording to the twelfth embodiment will be described.

First, conversion of the magnitude of a current by the transmission linetransformer will be described. Differential signals are transmitted froma pair of the first differential signal ports 110P and 110N to a pair ofthe second differential signal ports 111P and 111N. At this time, thehigh-frequency signal transmitted through the main line 101 of the firsttransmission line group 100P and the high-frequency signal transmittedthrough the main line 101 of the second transmission line group 100Nhave phases opposite to each other. In FIG. 21, the phases opposite toeach other of the high-frequency signals are represented by arrowsindicating the directions opposite to each other.

An alternating current flowing through the first line 101A and thesecond line 101B induces an odd-mode current flowing through the subline 102. The direction of the current flowing through the first line101A from the first end portion E1 toward the mutual connection point PIis the same as the direction of the current flowing through the secondline 101B from the mutual connection point PI toward the second endportion E2. The direction of the current flowing through the sub line102 is opposite to the direction of the current flowing through thefirst line 101A and the second line 101B. The magnitude of the currentflowing through the sub line 102 is twice the magnitude of the currentflowing through the first line 101A and the second line 101B. Themagnitude of the current flowing through the first line 101A and thesecond line 101B is represented by i, whereas the magnitude of thecurrent flowing through the sub line 102 is represented by 2i.

Because the direction of the current flowing through the main line 101of the first transmission line group 100P is opposite to the directionof the current flowing through the main lint 101 of the secondtransmission line group 100N, the direction of the current flowingthrough the sub line 102 of the first transmission line group 100P isthe same as the direction of the current flowing through the main line101 of the second transmission line group 100N. Thus, the currentflowing through the main line 101 of the second transmission line group100N and the current flowing through the sub line 102 of the firsttransmission line group 100P are added together, and the current flowingfrom the first end portion E1 of the main line 101 of the secondtransmission line group 100N toward the first differential signal port110N has a magnitude of 3i.

Similarly, the current flowing from the first differential signal port110P toward the first end portion E1 of the main line 101 of the firsttransmission line group 100P has a magnitude of 3i. The currents of thedifferential signals output to the pair of second differential signalports 111P and 111N have a magnitude of i. In this way, the magnitudesof the currents of the differential signals are converted to bemultiplied by ⅓ by the transmission line transformer according to thetwelfth embodiment. On the other hand, in the case of transmittingdifferential signals from the second differential signal ports 111P and111N to the first differential signal ports 110P and 110N, themagnitudes of the currents are converted to be multiplied by three.

Next, voltage transformation by the transmission line transformer willbe described. The potentials at the first differential signal port 110Pand the first differential signal port 110N are +v and −v, respectively.The potential difference between the pair of first differential signalports 110P and 110N is 2v. The potentials at the second end portions E2of the two sub lines 102 are represented by v₀. The potential at thefirst end portion E1 of the main line 101 of the first transmission linegroup 100P and the potential at the first end portion E1 of the sub line102 of the second transmission line group 100N are both +v. Thepotential at the first end portion E1 of the main line 101 of the secondtransmission line group 100N and the potential at the first end portionE1 of the sub line 102 of the first transmission line group 100P areboth −v.

Because the coupling between the first line 101A and the sub line 102 isequivalent to the coupling between coils having the same number ofturns, the potential difference between both ends of the first line 101Ais equal to the potential difference between both ends of the sub line102. The potential difference between both ends of the sub line 102 ofthe first transmission line group 100P is v₀+v, and thus the potentialat the mutual connection point PI of the first line 101A of the firsttransmission line group 100P is v₀+2v. The potential at the mutualconnection point PI of the second line 101B of the first transmissionline group 100P is also v₀+2v. Similarly, the potential at the mutualconnection point PI of the second line 101B of the second transmissionline group 100N is v₀−2v.

Because the coupling between the second line 101B and the sub line 102is equivalent to the coupling between coils having the same number ofturns, the potential difference between both ends of the second line101B is equal to the potential difference between both ends of the subline 102. The potential difference between both ends of the sub line 102of the first transmission line group 100P is v₀+v, and thus thepotential at the second end portion E2 of the second line 101B of thefirst transmission line group 100P is 2v₀+3v. Similarly, the potentialat the second end portion E2 of the second line 101B of the secondtransmission line group 100N is 2v₀−3v. Thus, the potential differencebetween the pair of second differential signal ports 111P and 111N is6v.

In this way, the magnitudes of the voltages of the differential signalsare converted to be multiplied by three by the transmission linetransformer according to the twelfth embodiment. On the other hand, inthe case of transmitting differential signals from the seconddifferential signal ports 111P and 111N to the first differential signalports 110P and 110N, the magnitudes of the voltages are converted to bemultiplied by ⅓.

When a load is connected between the pair of second differential signalports 111P and 111N, the impedance seen on the load side from the pairof first differential signal ports 110P and 110N is 1/9 times as much asthe impedance seen on the load side from the second differential signalports 111P and 111N. On the other hand, when a load is connected betweenthe pair of first differential signal ports 110P and 110N, the impedanceseen on the load side from the pair of second differential signal ports111P and 111N is 9 times as much as the impedance seen on the load sidefrom the first differential signal ports 110P and 110N. In this way, thetransmission line transformer according to the twelfth embodimentfunctions as an impedance transformation circuit of the differentialtransmission lines.

FIG. 22 is an exploded perspective view of the transmission linetransformer according to the twelfth embodiment. The transmission linetransformer according to the twelfth embodiment includes three metalliclayers disposed in a substrate. The first line 101A and the second line101B of each of the first transmission line group 100P and the secondtransmission line group 100N are formed of metallic patterns disposed atdifferent positions in the thickness direction of the substrate. Forexample, the first line 101A is disposed in an uppermost layer and thesecond line 101B is disposed in a lowermost layer. The sub line 102 isformed of a metallic pattern disposed between the first line 101A andthe second line 101B in the thickness direction of the substrate. Thefirst line 101A, the second line 101B, and the sub line 102 each have asubstantially spiral shape in which the number of turns is about 2.

The first end portion E1 of the first line 101A is located on an outerside of the substantially spiral shape, and the mutual connection pointPI is located on an inner side of the substantially spiral shape. Themutual connection point PI of the second line 101B is located on aninner side of the substantially spiral shape, and the second end portionE2 is located on an outer side of the substantially spiral shape. Thefirst end portion E1 and the second end portion E2 of the sub line 102are located on an outer side and an inner side of the substantiallyspiral shape, respectively. The metallic patterns forming the firsttransmission line group 100P and the metallic patterns forming thesecond transmission line group 100N have a mirror symmetry relationship.

When viewed from an upper surface side of the substrate, the first line101A of the first transmission line group 100P extends to turncounterclockwise from the first end portion E1 toward the mutualconnection point PI, and the second line 101B extends to turncounterclockwise from the mutual connection point PI toward the secondend portion E2. The sub line 102 of the first transmission line group100P extends to turn counterclockwise from the first end portion E1toward the second end portion E2. In the second transmission line group100N, the turn directions of the metallic patterns of the substantiallyspiral shapes are opposite to the turn directions of the correspondingmetallic patterns of the first transmission line group 100P. Asdescribed above, in the first line 101A, the sub line 102, and thesecond line 101B coupled to each other, the turn directions from the endportions corresponding to each other toward the other end portions arethe same.

Metallic patterns extend from the first end portions E1 of the firstlines 101A of the first transmission line group 100P and the secondtransmission line group 100N to the first differential signal ports 110Pand 110N. Similarly, metallic patterns extend from the second endportions E2 of the second lines 101B of the first transmission linegroup 100P and the second transmission line group 100N to the seconddifferential signal ports 111P and 111N.

Furthermore, pads 112P, 112N, 113P, 113N, 114P, and 114N for externalconnection are disposed in the uppermost layer. The pads 112P and 112Nare connected to the first differential signal ports 110P and 110N,respectively. The mutual connection point PI of the first line 101A isconnected to the mutual connection point PI of the second line 101B viaan interlayer connection conductor 130.

The second differential signal port 111P in the lowermost layer and thepad 113P for external connection in the uppermost layer are connected toeach other via a capacitor Cbk1. Similarly, the second differentialsignal port 111N and the pad 113N for external connection are connectedto each other via a capacitor Cbk2. As each of the capacitors Cbk1 andCbk2, for example, a capacitance element having a metal-insulator-metal(MIM) structure is used.

The first end portion E1 of the first line 101A of the firsttransmission line group 100P is connected to the first end portion E1 ofthe sub line 102 of the second transmission line group 100N via aninterlayer connection conductor 131. The first end portion E1 of thefirst line 101A of the second transmission line group 100N is connectedto the first end portion E1 of the sub line 102 of the firsttransmission line group 100P via another interlayer connection conductor131.

The second end portion E2 of the sub line 102 of the first transmissionline group 100P is connected to the pad 114P for external connection viaan interlayer connection conductor 132. The second end portion E2 of thesub line 102 of the second transmission line group 100N is connected tothe pad 114N for external connection via another interlayer connectionconductor 132. The pads 114P and 114N for external connection areconnected to each other by an external wiring line 140. The externalwiring line 140 is disposed in or on a module substrate on which thetransmission line transformer is mounted, for example. The pads 114P and114N for external connection function as a connection structure forconnecting the second end portions E2 of the two sub lines 102.

A capacitor Cmn is connected between the pads 112P and 112N. As thecapacitor Cmn, for example, a capacitance element having an MIMstructure is used.

FIG. 23 is a diagram illustrating the positional relationship of themetallic patterns of the transmission line transformer according to thetwelfth embodiment in plan view. In FIG. 23, the metallic pattern in theuppermost layer is depicted with a relatively thick contour line, themetallic pattern in the intermediate layer is hatched relativelydensely, and the metallic pattern in the lowermost layer is hatchedrelatively roughly.

The first line 101A, the second line 101B, and the sub line 102 overlapeach other in most portions in plan view. As described with reference toFIG. 22, the first line 101A, the second line 101B, and the sub line 102of the first transmission line group 100P and the first line 101A, thesecond line 101B, and the sub line 102 of the second transmission linegroup 100N have a mirror symmetry relationship.

In plan view, the pads 112P and 112N each have a protruding portionextending toward the other pad. The two protruding portions areconnected to each other via the capacitor Cmn.

The capacitor Cbk1 is disposed in a region where the second differentialsignal port 111P in the lowermost layer and the pad 113P in theuppermost layer overlap each other, and the capacitor Cbk2 is disposedin a region where the second differential signal port 111N in thelowermost layer and the pad 113N in the uppermost layer overlap eachother. The capacitors Cbk1 and Cbk2 may each include the metallicpattern in the intermediate layer.

FIG. 24 is an equivalent circuit diagram of a transmission linetransformer 150 according to the twelfth embodiment. The configurationof the transmission lines from the first differential signal ports 110Pand 110N to the second differential signal ports 111P and 111N is thesame as the configuration in the schematic diagram illustrated in FIG.21. As described with reference to FIG. 22, the transmission linetransformer 150 includes the plurality of pads 112P, 112N, 113P, 113N,114P, and 114N for external connection.

The first differential signal ports 110P and 110N are connected to thepads 112P and 112N, respectively. The capacitor Cmn is connected betweenthe first differential signal ports 110P and 110N. The capacitor Cmn isan additional element to achieve impedance matching. The seconddifferential signal ports 111P and 111N are connected to the pads 113Pand 113N via the capacitors Cbk1 and Cbk2, respectively.

The second end portions E2 of the sub lines 102 of the respective firsttransmission line group 100P and second transmission line group 100N areconnected to the pads 114P and 114N, respectively. The pads 114P and114N are connected to each other by the external wiring line 140.

Next, excellent effects of the twelfth embodiment will be described.

In the twelfth embodiment, the current induced in the sub line 102 bythe current flowing through the main line 101 (FIG. 21) connected to oneof the two transmission lines constituting differential transmissionlines is superimposed on the current flowing through the othertransmission line. Accordingly, the magnitude of the current isconverted between the first differential signal ports 110P and 110N onone side and the second differential signal ports 111P and 111N on theother side.

The second end portions E2 of the two sub lines 102 are connected toeach other, and the potential v₀ at the second end portions E2 of thesub lines 102 (FIG. 21) serves as a reference potential of the twotransmission lines constituting the differential transmission lines.With reference to the potential v₀ serving as a reference potential, thevoltage between the second differential signal ports 111P and 111N isspecified by the voltage between the first differential signal ports110P and 110N. Furthermore, voltage transformation is performed asdescribed with reference to FIG. 21.

In this way, the current and voltage are transformed between the firstdifferential signal ports 110P and 110N on one side and the seconddifferential signal ports 111P and 111N on the other side, and thusimpedance transformation can be performed in the differentialtransmission lines. In addition, as in the first embodiment, it ispossible to suppress an increase in the size of the impedancetransformation circuit and to increase the impedance transformationratio.

A modification example of the twelfth embodiment will be described.

In the twelfth embodiment, the number of turns of each of the first line101A, the second line 101B, and the sub line 102 is about 2.Alternatively, the number of turns may be other than 2, for example, 1.

In the twelfth embodiment, the coupling between the first line 101A andthe sub line 102 and the coupling between the second line 101B and thesub line 102 are equivalent to the coupling between coils having thesame number of turns. As a modification example of the twelfthembodiment, at least one of the coupling between the first line 101A andthe sub line 102 and the coupling between the second line 101B and thesub line 102 may be equivalent to the coupling between coils having adifferent number of turns, like the coupling between the secondtransmission line 22 and the third transmission line 23 in the secondembodiment illustrated in FIGS. 3A and 3B. As a result of changing theratio of the number of turns of the coupling between the first line 101Aand the sub line 102 or the ratio of the number of turns of the couplingbetween the second line 101B and the sub line 102, the impedancetransformation ratio can be changed.

In the foregoing embodiment, the two sub lines 102 are connected to eachother by the external wiring line 140 by using the connection structureformed of the pads 114P and 114N for external connection (FIG. 22). As amodification example of the twelfth embodiment, four layers of metallicpatterns may be disposed in the substrate, and the second end portionsE2 of the two sub lines 102 may be connected to each other by a wiringline formed of a metallic pattern in the substrate. In this case, thewiring line formed of the metallic pattern connecting the two sub lines102 may be regarded as the connection structure for the sub lines 102.

Thirteenth Embodiment

An amplifying module according to a thirteenth embodiment will bedescribed with reference to FIG. 25. The amplifying module according tothe thirteenth embodiment includes the transmission line transformeraccording to the twelfth embodiment mounted therein.

FIG. 25 is an equivalent circuit diagram of the amplifying moduleaccording to the thirteenth embodiment. The amplifying module accordingto the thirteenth embodiment has a two-stage configuration including adriver-stage amplifying circuit 160 and a power-stage amplifying circuit180. The driver-stage amplifying circuit 160 is a single-end amplifyingcircuit, whereas the power-stage amplifying circuit 180 is adifferential amplifying circuit. A first balun 151 is connected to theinput side of the power-stage amplifying circuit 180, and a second balun152 is connected to the output side thereof. The first balun 151 has thesame configuration as the transmission line transformer illustrated inFIG. 21, and the first differential signal ports 110P and 110N areconnected to the power-stage amplifying circuit 180. The second balun152 has the same configuration as the transmission line transformer 150illustrated in FIG. 24, and the first differential signal ports 110P and110N are connected to the power-stage amplifying circuit 180.

A high-frequency signal is input from an input terminal PAin through amatching circuit 170 to the driver-stage amplifying circuit 160. Thedriver-stage amplifying circuit 160 includes an input capacitor C1, abase bias circuit BB1, a base ballast resistor R1, and a transistor Q1.A power supply terminal Vcc1, a choke inductor L3, and a capacitor C3constitute a power supply circuit 161. Power is supplied from the powersupply terminal Vcc1 through the choke inductor L3 to the collector ofthe transistor Q1. The power supply terminal Vcc1 is connected to groundvia the capacitor C3.

The high-frequency single output from the driver-stage amplifyingcircuit 160 is input to the second differential signal port 111P of thefirst balun 151 through a capacitor C4. The second differential signalport 111N of the first balun 151 is connected to ground. Differentialsignals are output from the two first differential signal ports 110P and110N of the first balun 151. The first balun 151 functions as anunbalanced-balanced transformation circuit and an impedancetransformation circuit.

The differential signals output from the first balun 151 are input tothe power-stage amplifying circuit 180. The power-stage amplifyingcircuit 180 includes transistors Q5 and Q6, input capacitors C5 and C6,base ballast resistors R5 and R6, and a base bias circuit BB2. A powersupply terminal Vcc2, choke inductors L7 and L8, and a capacitor C7constitute a power supply circuit 181. Power is supplied from the powersupply terminal Vcc2 through the choke inductor L7 to the collector ofthe transistor Q5, and power is supplied from the power supply terminalVcc2 through the choke inductor L8 to the collector of the transistorQ6. The power supply terminal Vcc2 is connected to ground via thecapacitor C7.

The differential signals output from the power-stage amplifying circuit180 are input to the first differential signal ports 110P and 110Nthrough the pair of pads 112P and 112N of the second balun 152. Thesecond differential signal port 111P on the output side of the secondbalun 152 is connected to an output terminal PAout via the capacitorCbk1 and the pad 113P. The second differential signal port 111N on theoutput side of the second balun 152 is connected to ground via thecapacitor Cbk2 and the pad 113N. The pair of pads 113P and 113N areconnected to each other via an inductor L9. The inductor L9 is anadditional element to achieve impedance matching. A single-end signal isoutput from the output terminal PAout. The second balun 152 functions asa balanced-unbalanced transformation circuit and an impedancetransformation circuit.

Next, excellent effects of the thirteenth embodiment will be described.In the thirteenth embodiment, impedance matching can be achieved on theinput side and output side of the power-stage amplifying circuit 180 byusing the transmission line transformer according to the twelfthembodiment. As in the twelfth embodiment, it is possible to suppress anincrease in the sizes of the first balun 151 and the second balun 152and to increase the impedance transformation ratio.

A modification example of the thirteenth embodiment will be describedwith reference to FIG. 26.

FIG. 26 is an equivalent circuit diagram of an amplifying moduleaccording to a modification example of the thirteenth embodiment. Inthis modification example, a differential amplifying circuit is used aseach of the driver-stage amplifying circuit 160 and the power-stageamplifying circuit 180. The driver-stage amplifying circuit 160 includestransistors Q1 and Q2, input capacitors C1 and C2, base ballastresistors R1 and R2, and the base bias circuit BB1. A third balun 153 isconnected to the input side of the driver-stage amplifying circuit 160.An interstage matching circuit 154 is connected to the input side of thepower-stage amplifying circuit 180, and a fifth balun 155 is connectedto the output side of the power-stage amplifying circuit 180.

The third balun 153 has the same configuration as the first balun 151 ofthe amplifying module illustrated in FIG. 25 and functions as anunbalanced-balanced transformation circuit and an impedance matchingcircuit. The power supply circuit 161 connected to the output side ofthe driver-stage amplifying circuit 160 has the same configuration asthe power supply circuit 181 illustrated in FIG. 25. The interstagematching circuit 154 has the same configuration as the transmission linetransformer illustrated in FIG. 21. The second differential signal ports111P and 111N (FIG. 21) serve as input ports, and the first differentialsignal ports 110P and 110N serve as output ports.

The differential signals output from the interstage matching circuit 154are input to the power-stage amplifying circuit 180. The circuitconfiguration of the stage subsequent to the power-stage amplifyingcircuit 180 is the same as the circuit configuration of the amplifyingmodule according to the thirteenth embodiment illustrated in FIG. 25.

Another modification example of the thirteenth embodiment will bedescribed with reference to FIG. 27.

FIG. 27 is an equivalent circuit diagram of an amplifying moduleaccording to another modification example of the thirteenth embodiment.The modification example illustrated in FIG. 27 is different from themodification example illustrated in FIG. 26 in the configurations of thepower supply circuits 161 and 181. Other than this, the configurationsaccording to both the modification examples are the same.

In the modification example illustrated in FIG. 27, the power supplycircuit 161 includes the power supply terminal Vcc1, an inductor L10,and a capacitor C10. The power supply terminal Vcc1 is connected to thesecond end portions E2 of the two sub lines 102 of the interstagematching circuit 154 via the inductor L10 and the wiring line 140. Thepower supply terminal Vcc1 is also connected to ground via the capacitorC10.

Power is supplied from the power supply terminal Vcc1 to the collectorof the transistor Q2 of the driver-stage amplifying circuit 160 throughthe inductor L10, the sub line 102 of the first transmission line group100P, and the main line 101 of the second transmission line group 100N.Similarly, power is supplied from the power supply terminal Vcc1 to thecollector of the transistor Q1 of the driver-stage amplifying circuit160 through the inductor L10, the sub line 102 of the secondtransmission line group 100N, and the main line 101 of the firsttransmission line group 100P. In this way, power is supplied from thepower supply circuit 161 to the driver-stage amplifying circuit 160thorough the interstage matching circuit 154.

Because the first transmission line group 100P and the secondtransmission line group 100N function as an inductor, the inductor L10may be omitted. The inductor L10 and the capacitor C10 are additionalelements to achieve impedance matching.

Similarly, power is supplied from the power supply circuit 181 to thepower-stage amplifying circuit 180 through the fifth balun 155.

Also in the modification examples illustrated in FIGS. 26 and 27, as inthe thirteenth embodiment, it is possible to suppress an increase in thesize of the balun or the impedance matching circuit and to increase theimpedance transformation ratio.

The above-described embodiments are examples, and configurationsaccording to different embodiments can be partially replaced orcombined. Similar functions and effects of similar configurationsaccording to a plurality of embodiments are not mentioned for eachembodiment. The present disclosure is not limited to the above-describedembodiments. It would be obvious to those skilled in the art thatvarious changes, improvements, combinations, and the like can be made.

While preferred embodiments of the disclosure have been described above,it is to be understood that variations and modifications will beapparent to those skilled in the art without departing from the scopeand spirit of the disclosure. The scope of the disclosure, therefore, isto be determined solely by the following claims.

What is claimed is:
 1. A transmission line transformer comprising: asubstrate; and a first transmission line group and a second transmissionline group that are disposed in the substrate, wherein: the firsttransmission line group and the second transmission line group eachcomprise a main line and a sub line, the main line of the firsttransmission line group and the main line of the second transmissionline group each comprise a first line and a second line that aredisposed at different positions in a thickness direction of thesubstrate, the sub line of the first transmission line group is disposedbetween the first line and the second line of the first transmissionline group in the thickness direction of the substrate, the sub line ofthe second transmission line group is disposed between the first lineand the second line of the second transmission line group in thethickness direction of the substrate, the first line, the second line,and the sub line of the first transmission line group comprise portionsthat overlap each other when the substrate is viewed in a plan view, thefirst line, the second line, and the sub line of the second transmissionline group comprise portions that overlap each other when the substrateis viewed in the plan view, the sub line of the first transmission linegroup is electromagnetically coupled to the first line and the secondline of the first transmission line group, the sub line of the secondtransmission line group is electromagnetically coupled to the first lineand the second line of the second transmission line group, the sub lineof the first transmission line group comprises a first end portionconnected to a first end portion of the main line of the secondtransmission line group, the sub line of the second transmission linegroup comprises a first end portion connected to a first end portion ofthe main line of the first transmission line group, the sub line of thefirst transmission line group comprises a second end portion opposite tothe first end portion of the sub line of the first transmission linegroup, the sub line of the second transmission line group comprises asecond end portion opposite to the first end portion of the sub line ofthe second transmission line group, and the transmission linetransformer further comprises a connection structure that connects thesecond end portion of the sub line of the first transmission line groupto the second end portion of the sub line of the second transmissionline group.
 2. The transmission line transformer according to claim 1,wherein an alternating current flowing through the first line of thefirst transmission line group and an alternating current flowing throughthe second line of the first transmission line group induce an odd-modecurrent flowing through the sub line of the second transmission linegroup, and wherein an alternating current flowing through the first lineof the second transmission line group and an alternating current flowingthrough the second line of the second transmission line group induce anodd-mode current flowing through the sub line of the first transmissionline group.
 3. The transmission line transformer according to claim 2,wherein the first line, the second line, and the sub line of the firsttransmission line group and the first line, the second line, and the subline of the second transmission line group all comprise a substantiallyspiral-shaped portion.
 4. The transmission line transformer according toclaim 3, wherein the connection structure comprises a wiring line thatconnects the second end portion of the sub line of the firsttransmission line group to the second end portion of the sub line of thesecond transmission line group.
 5. The transmission line transformeraccording to claim 2, wherein the connection structure comprises awiring line that connects the second end portion of the sub line of thefirst transmission line group to the second end portion of the sub lineof the second transmission line group.
 6. The transmission linetransformer according to claim 1, wherein the first line, the secondline, and the sub line of the first transmission line group and thefirst line, the second line, and the sub line of the second transmissionline group all comprise a substantially spiral-shaped portion.
 7. Thetransmission line transformer according to claim 6, wherein theconnection structure comprises a wiring line that connects the secondend portion of the sub line of the first transmission line group to thesecond end portion of the sub line of the second transmission linegroup.
 8. The transmission line transformer according to claim 1,wherein the connection structure comprises a wiring line that connectsthe second end portion of the sub line of the first transmission linegroup to the second end portion of the sub line of the secondtransmission line group.